System and method for making correlation measurements utilizing pulse shape measurements

ABSTRACT

A receiver utilizes an array of complex accumulation registers to form an image of the average chip shape or, as appropriate, chip edge shape, of the received signal over a specified period of time as a time series of complex power measurements. The receiver divides the length of the chip into a plurality of ranges, or “bins, and, as appropriate, extends the bins to cover additional chips or portions thereof.” When a sample is taken, the receiver enables the respective registers that are associated with the corresponding bin or bins, and the respective registers then accumulates the associated power measurement. The receiver uses the accumulated measurements from selected registers and/or selected groups of registers, to produce the correlation values that are needed to perform one or more correlation techniques and/or one or more multipath mitigation techniques. As appropriate, the sizes and/or starting points of the bins, and/or the selections of the bins for the various groupings may be altered, to change the spacings, locations, and so forth to which correlation values correspond.

CROSS-REFERENCE TO RELATED APPLICATIONS

The present application is related to U.S. patent application Ser. No.10/823,030 entitled APPARATUS FOR AND METHOD OF MAKING PULSE-SHAPEDMEASUREMENTS.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The invention relates generally to systems for making correlationmeasurements using broadcast spread-spectrum signals and, in particular,to systems that make correlation measurements using pulse shapemeasurements.

2. Background Information

One example of a system that utilizes broadcast spread-spectrum signalsis a global positioning system, such as, GPS, GLONASS or GALILEOsystems. The system receivers determine their global positions based onthe signals they receive from associated satellites. The broadcastspread-spectrum signal consists of a carrier that is modulated by atleast one pseudorandom code, such as a binary PRN code that consists ofa pseudo-random sequence of ones and zeros that periodically repeat. Theones and zeros in the PRN code are referred to as “code chips,” and thetransitions in the code from one to zero or zero to one, which occur at“code chip times,” are referred to as “chip transitions.” Each satelliteuses a unique PRN code, and thus, a receiver can associate a receivedsignal with a particular satellite by determining which PRN code isincluded in the signal.

The receiver calculates the difference between the time a satellitetransmits its signal and the time that the receiver receives the signal.The receiver then calculates its distance, or “pseudo-range,” from thesatellite based on the associated time difference. Using thepseudo-ranges from at least four satellites, the receiver determines itsglobal position.

To determine the time difference, the receiver synchronizeslocally-generated PRN codes with the PRN codes in the received signal byaligning the code chips in respective local codes with the chips in thecorresponding satellite generated PRN codes. It then determines how muchthe locally-generated PRN codes are shifted, in time, from the knowntiming of the satellite PRN codes at the time of transmission, andcalculates the associated pseudoranges essentially by multiplying themeasured time shifts by the speed of light. The more closely thereceiver aligns the locally-generated PRN code with the PRN code in thereceived signal, the more precisely the receiver can determine theassociated time difference and pseudorange and, in turn, its globalposition.

The code synchronization operations include acquisition of the satellitePRN code and tracking the code. To acquire the PRN code, the receivergenerally makes a series of correlation measurements that are separatedin time by, for example, a code chip, to determine when thelocally-generated code aligns with the received code to within one codechip. To thereafter track the PRN code, the receiver generally makescorrelation measurements that are associated with the received PRN codeand early and late versions of the locally-generated PRN code. Using theearly and late correlation measurements, the receiver produces anassociated error signal that is proportional to the misalignment betweenthe local PRN code and the received PRN code. The error signal is used,in turn, to control the clocking speed of the local PRN code generator,which essentially shifts the local PRN code to minimize the errorsignal.

The receiver also typically aligns the satellite carrier with a localcarrier using correlation measurements associated with a punctualversion of the local PRN code. To do this the receiver uses a carriertracking phase lock loop.

The receiver receives not only line-of-sight, or direct path, satellitesignals but also multipath signals, which are signals that travel alongdifferent paths and are reflected to the receiver from the ground,bodies of water, nearby buildings, etc. The multipath signals arrive atthe receiver after the direct-path signal and combine with thedirect-path signal to produce a distorted received signal. Thisdistortion of the received signal adversely affects code synchronizationoperations because the correlation measurements, which measure thecorrelation between the local PRN code and the received signal, arebased on the entire received signal—including the multipath componentsthereof. The distortion may be such that the receiver attempts tosynchronize to a multipath signal instead of to the direct-path signal.One way to more accurately synchronize the received and thelocally-generated PRN codes is to use the “narrow correlators” discussedin U.S. Pat. Nos. 5,101,416; 5,390,207 and 5,495,499. It has beendetermined that narrowing the delay spacing between early and latecorrelation measurements substantially reduces the adverse effects ofnoise and multipath signal distortion on the early-minus-latemeasurements. The narrow correlators are essentially spaced closer to acorrelation peak that is associated with the punctual PRN codecorrelation measurements than the contributions of many of the multipathsignals. Accordingly, the early-minus-late correlation measurements madeby these correlators are significantly less distorted than they would beif they were made at a greater interval around the peak.

Another correlation technique makes non-zero correlation measurementsnear chip transitions in the locally-generated PRN code and zero valuedcorrelation measurements otherwise. This technique, which is referred toherein as “blanked correlation,” is described in U.S. Pat. No.6,243,409.

Yet another way to more accurately synchronize the received and thelocally-generated PRN codes is to use a multipath mitigation processingtechnique that iteratively produces estimates of the direct path signaland one or more of the multipath signals. One such technique, which usesmultiple correlators arranged on either side of the correlation peak isdescribed in U.S. Pat. Nos. 5,615,232 and 5,692,008. Another techniquethat uses multiple correlators is described in U.S. Pat. No. 5,414,729.Yet another multipath mitigation technique is discussed in Weill,“Multipath Mitigation Using Modernized GPS Signals: How Good Can ItGet,” ION GPS 2002, Portland, Oreg., Sep. 24-27, 2002.

The receivers and, in particular, the correlation hardware used forsignal acquisition and tracking are constructed to operate with selectedcorrelation and multipath mitigation schemes. Thus, a receiver thatoperates with conventional parallel early, punctual and late correlatorspositioned about the correlation peak includes the three correlators andassociated circuitry that provides the corresponding early, punctual andlate versions of the local PRN code. If the receiver instead usesmultiple early and late correlators, the receiver includes a sufficientnumber of the correlators and the circuitry required to produce theassociated versions of the local code. If a different correlation and/ormultipath mitigation technique is to be used, the receiver hardware musttypically be re-designed to include the necessary correlators and/or thecircuitry required to produce the corresponding local versions of thePRN code.

Also, a receiver using the narrow correlation technique discussed abovemay require an additional set of more widely spaced correlators for usein re-acquiring the GPS code if the narrowly spaced correlators shouldlose lock during tracking. Thus, such a system requires two sets ofearly and late correlators as well as the associated circuitry toproduce the corresponding versions of the GPS code.

SUMMARY OF THE INVENTION

The invention is a receiver that utilizes an array of complexaccumulation registers to perform any number of correlation andmultipath mitigation techniques and/or use essentially any desired delayspacing for single or multiple sets of early and late correlationmeasurements. The array of correlators forms an image of the averagechip shape or, as appropriate, chip edge shape, of the received signalover a specified period of time. The image is expressed as a time seriesof complex power measurements along the length of a single chip or alonga chip edge, as appropriate. The receiver manipulates selected powermeasurements and/or groups of selected power measurements to produce thedesired correlation discrimination information, and thus, eliminates theneed for the conventional parallel early and late correlator hardwareand the associated circuitry for producing the corresponding versions ofthe local PRN code.

More specifically, the receiver includes in a receiver channel an arrayof complex accumulation registers. Each complex accumulation register,which consists of an in-phase accumulator and a quadrature phaseaccumulator, can be separately and selectively enabled. The respectivecomplex accumulation registers accumulate measurements that areassociated with signal samples that are taken from specific ranges oflocations along a spread-spectrum chip, or at corresponding relative“code phase times”. The array further includes a complex accumulationregister that is only enabled when there is no chip transition in thelocal code, such that the “non-transition” accumulation registercollects measurements that contain essentially only phase tackinginformation, or signal power.

The receiver divides the length of the chip into a plurality of ranges,or “bins,” that correspond to fractions of a chip. The bins may but neednot be the same size across the chip. When a sample is taken, thereceiver enables the complex accumulation register that is associatedwith the corresponding bin. The enabled register then accumulates therelated correlation measurement. As discussed in more detail below, thecomplex accumulation registers collect the measurements at sample timesthat are asynchronous with the code rate, and the ranges and thecorresponding sizes and/or numbers of bins are thus fully adjustable.Accordingly, the hardware can be used with essentially any iscorrelation and/or multipath mitigation scheme by selectively adjustingthe sizes of the ranges and/or combining the measurements associatedwith selected ranges, to provide appropriate discrimination informationfor code and carrier tracking and, as appropriate, multipath mitigation.

The same set of accumulated measurements may be selectively grouped toproduce correlation values for various correlation techniquesconcurrently. Thus, the receiver may, using the same set of accumulatedmeasurements, produce correlation values for one or more correlationtechniques including wide spacing, narrow spacing, blanked correlation,multiple correlators, and so forth, and/or one or more multipathmitigation techniques.

As an example, the accumulated correlation measurements associated witha selected number of bins both before and after a desired code trackingpoint may be combined to produce early and late correlation values foressentially any desired delay spacing. Further, multiple early and latecorrelation values at desired spacings may be determined by selectivelycombining the accumulated correlation measurements associated withvarious groups of bins that either precede or come after the desiredcode tracking point, and so forth.

BRIEF DESCRIPTION OF THE DRAWINGS

The invention description below refers to the accompanying drawings, ofwhich:

FIG. 1 is a block diagram of a spread-spectrum receiver that employs theteachings of the inventions;

FIG. 2 is a more-detailed block diagram of a complex accumulationregister that is included in the receiver of FIG. 1;

FIG. 3 is an alternative arrangement of a code phase decoder included inthe receiver of FIG. 1;

FIG. 4 is a plot of accumulated correlation measurements;

FIGS. 5A and 5B are illustrations of code chip ranges; FIG. 6 is a moredetailed block diagram of the code phase decoder included in thereceiver of FIG. 1; and

FIG. 7 is a block diagram of the receiver of FIG. 1 further includingmultipath mitigation processing elements.

DETAILED DESCRIPTION OF AN ILLUSTRATIVE EMBODIMENT

Referring to FIG. 1, a receiver 10 receives a composite spread spectrumsignal over an antenna 11. A downconverter 12 and sampler 14 operate ina conventional manner, to downconvert the received composite signal and,in the exemplary embodiment, take sequential I and Q samples of thedownconverted signal and convert them to digital values. The sequentialsamples are provided to the respective channels 16 as successive I and Qsamples. For convenience, a single channel 16 is depicted in thedrawing.

The channel 16 includes a complex mixer 25 that removes the carrier fromthe I and Q samples by mixing them with an estimate of the carrier thatis produced by a carrier NCO 26. The respective incoming I and Q samplesare mixed with both sine and cosine transformations of the estimatedcarrier, to produce corresponding complex I and Q sample pairs.

As discussed in more detail below, the sample pair for a given I or Qsample is correlated with, that is, multiplied by, a locally-generatedPRN code and the results are accumulated in inphase and quadratureaccumulators 38 (FIG. 2) of an enabled complex accumulation register 34in an array 32 of complex accumulation registers. The enabled complexaccumulation register is associated with the sample's code phase time,or more specifically, with a range of times that include the code phasetime of the sample. The range may be referred to herein also as a “bin.”The component pairs corresponding to the respective I and Q samples areused to more precisely characterize the samples, which may include bothreal and imaginary components. The correlation measurements areaccumulated over a number of code chip edges, such that the complexaccumulation registers in the array contain measurements that correspondto an average chip shape or, as appropriate, average chip edge shape.

A non-transition complex accumulation register 36 accumulates the signalpower measurements over the respective code chips in which there are nocorresponding transitions, i.e., changes in polarity, at the chip timesin the local code. These correlation measurements have essentially nocode shape information, and contribute only to the total correlationpower. Accordingly, the accumulated values in the non-transition complexaccumulation register are used directly in the calculations relating tocarrier phase tracking and as part of the punctual correlation value inthe calculations relating to code tracking, as discussed in more detailbelow.

The carrier NCO includes a phase generator 22 that produces the carrierphase estimate. The phase generator 22 operates in a known manner andincorporates, through an adder 23, updated carrier rate information thatis provided by a carrier rate register 25. The carrier rate register is,in turn, controlled by a carrier tracking error signal that is producedby a phase locked loop (“PLL”) 60.

The channel 16 further includes a PRN code generator 24, which operatesin a known manner to produce a locally-generated spread-spectrum PRNcode that corresponds to one of the codes in the received compositesignal. In the example of a GPS system, the code generator 24 produces alocally-generated PRN code that is the same as the code that istransmitted by one of the satellites then in view. In the exemplaryreceiver, the code generator 24 produces only an “early” version of thePRN code, that is, a version that precedes the PRN code that istransmitted by the satellite by a predetermined fraction of a code chip.The local PRN code may precede the transmitted code by 1 code chip, orone-half code chip, and so forth. For convenience, we refer herein tothe locally produced early PRN code as the “local code,” since thereceiver requires only a single version of the PRN code. This is incontrast to conventional receivers, which require early, punctual andlate versions of the PRN code.

A code numerically controlled oscillator (“CNCO”) 42 drives the PRN codegenerator 24, to bring the local code into alignment with the receivedcode, such that the local code precedes the received code by thepredetermined code chip fraction. A code phase generator operates in aknown manner to produce an estimated code phase that incorporates,through an adder 45, updated code rate information from a code rateregister 46. The code rate register is, in turn, controlled by a codetracking error signal that is produced by a carrier-aided code trackingDLL 62, which operates in a conventional manner. As discussed below, theCNCO provides the estimated code phase to a code phase decoder 40, whichproduces signals that selectively enable the complex accumulationregisters 34 and 36.

The complex I and Q samples are multiplied by the local code inmultipliers 26 and 27, to produce corresponding correlation measurementsignals that are then provided to the array 32 of complex accumulationregisters 34 and 36. The code phase decoder 40 selectively enables theaccumulation registers, such that the correlator measurements areaccumulated in the appropriate accumulation registers or “bins,” thatis, in the accumulation registers that are associated with the codephase times that are estimated for the respective samples.

To save battery power, the code phase decoder may operate at one-halfthe sample rate. An offset register 41 (FIG. 3) is then included toupdate the code phase decoder appropriately between clock cycles. In theexample, the offset register is a Q offset register that provides offsetvalues to the code phase decoder 40 to ensure that the appropriateaccumulation registers 34 and 36 are enabled to receive the correlationmeasurements that correspond to the code phase times of the Q samples.

Referring still to FIG. 3, the carrier NCO may similarly operate atone-half the sample rate, and include a phase compensation circuit 28 toprovide to the mixer 25 the sine and cosine values for the respective Iand Q samples. The mixer then produces the respective complex samples asin-phase and quadrature component pairs:I_(TI)=I cos π_(TI)Q _(TI) =−I sin π_(TI)andI_(TQ)=Q sin π_(TQ)Q_(TQ)=Q cos π_(TQ)where TI refers to the code phase time of the incoming in-phase sample,TQ refers to the code phase time of the incoming quadrature-phasesample, π_(TI) is the estimated carrier phase angle at the time of theincoming in-phase sample and π_(TQ) is the estimated carrier phase angleat the time of the incoming quadrature-phase sample.

As discussed below, the receiver manipulates the accumulated valuescontained in respective complex accumulation registers 32 and 36 toproduce code tracking discriminator information that is used in the codetracking DLL 62 and phase tracking information that is used in thecarrier tracking PLL 60.

Referring now also to FIG. 4, the operations of the receiver aredescribed in terms of an example in which a standard early-minus-latediscriminator is used for the tracking of a GPS C/A code In the examplethe contents of the in-phase and quadrature accumulators provide theaverage C/A code chip edge shape, as depicted in FIG. 4 (RePAC I andRePAC Q signals). The tracking point selected for the C/A code chiptransition is the zero crossing of the inphase accumulated values, whichoccurs in the drawing, between bins 7 and 8. A code/carrier error signalprocessor 50 manipulates the accumulated correlation measurements forselected bins to produce code and carrier tracking error signals, asdescribed below.

The code/carrier error signal processor 50 calculates the standardearly-minus-late discriminator as: $\begin{matrix}{P_{E - L} = {\sum\limits_{k = {p - n + 1}}^{p + n}A_{k}}} & \left( {{eqn}.\quad 1} \right)\end{matrix}$where 2n is the desired early-late delay spacing represented as a numberof bins, p is the bin number that designates the desired code trackingpoint, i.e., the code tracking point falls between bins p and p+1, andA_(k) is the complex value contained in bin k's in-phase andquadrature-phase accumulators. The summation is a complex additionoperation, with the contents of the in-phase and the quadratureaccumulators of bin k as the real and the imaginary components,respectively, of the corresponding complex value A_(k). Further, thevalues A_(k) are normalized to accommodate different ranges or binsizes.

The processor 50 may use various values of n, that is, numbers of binson either side of the designated code tracking point, to produceearly-minus-late discriminator information associated with desiredcorrelator spacings. For example, the discriminator informationassociated with a narrower spacing is calculated using a smaller numberof bins, i.e., using a smaller value of n. Alternatively, or inaddition, the processor may reduce the sizes of the bins, that is,shorten the lengths of the associated ranges, such that combinations ofn early bins and n late bins produces a discriminator value thatcorresponds to a desired narrower early-late spacing. If a wider spacingis required to, for example, re-acquire the code, the processor mayinstead use a larger value for n, that is, use accumulated values fromgreater numbers of bins. Alternatively, or in addition, the processormay widen the bins. Further, the processor may change the startingpoints of the bins, such that the bins are moved to, for example,associate the code tracking point with the complex accumulation register34 that is in the center of the array 32.

Further, if the spacing of the bins, that is, the spacing between thestarting points of the bins or alternatively the mid-points of the bins,is greater than or equal to the spacing of samples taken at the Nyquestrate, the system may mathematically manipulate, for example,interpolate, between the accumulated values that correspond to the bins.This produces a chip edge shape with greater granularity, withoutsacrificing precision. The intermediate values, determined in theexample by the interpolation, may then be used in calculations in placeof or in addition to the accumulated values. Accordingly, the value “n”in the calculations is expanded to include intermediate bins whichcorrespond to the interpolated values. The selected delay spacing isthus not limited by the relative spacings or sizes of the bins that areassociated with the accumulation registers.

The code/carrier error processor 50 calculates the punctual accumulationvalue that is used for determining the code error signal as:$\begin{matrix}{P_{p} = {{\sum\limits_{k = {p + 1}}^{N}A_{k}} - {\sum\limits_{k = 1}^{p}A_{k}} + A_{NT}}} & \left( {{eqn}.\quad 2} \right)\end{matrix}$where p again designates the desired code tracking point, N is the totalnumber of transitional bins and A_(NT) is the complex value in the“non-transitional” accumulation register. The punctual correlation valuecould be determined without the accumulated non-transition value, thatis, without A_(NT). If, however, a GPS C/A code is being trackedone-half of the associated signal power is essentially lost withoutA_(NT) because the C/A code transitions at only one-half of the codechip times in a code epoch.

The code error, C_(error), from a standard Normalized Dot Product DLLDiscriminator is then: $\begin{matrix}{C_{error} = {\frac{{I_{P}I_{E - L}} + {Q_{P}Q_{E - L}}}{I_{P}^{2} + Q_{P}^{2}} \times {chipsize}}} & \left( {{eqn}.\quad 3} \right)\end{matrix}$where I_(P) and Q_(P) are, respectively, the in-phase andquadrature-phase components of the complex punctual accumulation valueP_(P) and I_(E-L) and Q_(E-L) are the in-phase and quadrature-phasecomponents of the complex early-minus-late discriminator, P_(E-L). Thechip size is included in the calculation to normalize the error value,since various codes, e.g., the GPS C/A code and P code, have differentchip sizes. The processor 50 provides the code error signal to the DLL62, which then operates in a conventional manner to produce the errorsignal that controls the code rate register 46.

The code/carrier error signal processor determines the carrier phaseerror using an arctangent-like function: $\begin{matrix}{{{Phase}\quad{Error}} = {\arctan\quad\left\lbrack \frac{\left( {{\sum\limits_{k = {p + 1}}^{N}I_{k}} - {\sum\limits_{k = 1}^{p}I_{k}} + I_{NT}} \right)^{2}}{\left( {{\sum\limits_{k = {p + 1}}^{N}Q_{k}} - {\sum\limits_{k = 1}^{p}Q_{k}} + Q_{NT}} \right)^{2}} \right\rbrack}} & \left( {{eqn}.\quad 4} \right)\end{matrix}$where I_(k) and Q_(k) are the in-phase and quadrature-phase componentsof the complex value that is contained in the complex accumulationregister that corresponds to bin k and I_(NT) and Q_(NT) are thein-phase and quadrature-phase components of the complex value that iscontained in the non-transitional complex accumulation register.

The phase error signal is used by the PLL 60 in a conventional manner,to produce the phase tracking error signal that controls the carrier NCOphase generator 22. The phase error calculation uses the accumulatedvalues from all of the complex accumulator registers, including the“non-transition” complex accumulation register 36. While the phase errorcould be determined without the accumulated non-transition value, asdiscussed above, one-half of the associated signal power is essentiallylost because the C/A code transitions at only one half of the code chiptimes in a code epoch.

Referring again to FIG. 1, the CNCO 42 produces chip-edge clock signalsthat are used to align the phase of the locally-generated PRN code tothe received PRN code, to within the predetermined fraction of a chip.The CNCO also produces fine code chip phase detail signals, whichrepresent the estimated code chip times of respective incoming I and/orQ samples, and provides these signals to the code phase decoder 40.

The code phase register 44 at any given time contains a count thatcorresponds to the estimated code phase, that is, to an estimated codephase time. When the count corresponds to the start of a new chip, thecode phase register provides a signal to the code generator 24, whichthen produces the next chip of the locally generated code. The signalproduced by the code phase register is synchronous with chip times inthe local PRN code, which in the example is the early code version. Atevery sample clock time the code phase register also provides the codephase time value to the code phase decoder 40, which controls theenabling of the complex accumulation registers 32.

Before discussing the operations of the code phase decoder 40 in moredetail, we refer to FIGS. 5A and 5B to describe the code chip rangesthat are associated with the accumulation registers 32. As shown in FIG.5A, a code chip 70 is segmented into a plurality of code chip ranges orbins 72, each of which is a fraction of a code chip. The sample s₁ takenat time t₁ has a code chip time that is included in a range that coversthe middle of the chip. The ranges near the chip rising edge may besmaller than the ranges that are near the middle of the chip, asappropriate.

Referring also to FIG. 5B, the bins 72, may extend up to the fallingedge of the chip, and bins 73 may extend beyond the falling edge of thechip and even over multiple chips. The bins 72 that cover the fallingedge and the bins 73, as appropriate, may be used in wide correlationtechniques, such as techniques that involve delay spacings of one ormore chips. For wide correlation the bins at or near the falling edge ofthe chip may be used to produce early signals or, with a flipped sign,late signals, depending on the desired spacing. The values from bins 73may be used to calculate correlation values that correspond to delayspacings of greater than 1 chip to provide a larger pull-in region forsignal acquisition and tracking in noisy and/or high dynamicenvironments. Further, as described in more detail with reference toFIG. 7 below, the values from bins associated with multiple chips mayalso be used to more fully characterize multipath signals.

Referring also to FIGS. 2 and 6, at each pulse of the sample clock, thecode phase register 44 provides to the code phase decoder 40 a codephase time value that corresponds to the estimated position of thecorresponding sample relative to the underlying code chip. Thus, atsample time t₁ (FIG. 4), the code phase register provides to the codephase decoder a code phase time value that corresponds to the sample'smid-chip position. As depicted in FIG. 6, the code decoder includes aplurality of bin processors 43 that collectively determine which bincontains the code phase that is estimated for the current sample. Theprocessor 43 that corresponds to the appropriate bin provides signalsthat enable the associated complex accumulation register 34, such thatthe register can then add the correlation measurement values to thecontents of the inphase and quadrature accumulators 38.

The processors 43 may, for example, compare the estimated code phasetime with upper and lower bin boundary values that define the range orextent of the bin in terms of code phase times. The upper and binboundary lower values may be readily altered, to enlarge or reduce theextent of the associated ranges. The bin boundary values may instead orin addition be selectively altered for particular bins to, for example,use smaller ranges for the bins that are nearest to the chip edge, andso forth.

The range upper and lower bin boundary values are provided by thecode/carrier error signal processor 50. The processor may adjust theranges based on the relative sizes of the code and phase errors. Theprocessor may, for example, reduce the sizes of certain or all of theranges once the code tracking error signal is sufficiently small toindicate tracking to with one code chip, and further reduce the rangesas the tracking error decreases. In addition, as discussed above, theprocessor may interpolate between bins to 1s provide correlation valuesthat are more closely spaced. In this way, the processor takes advantageof the increased tracking accuracies of narrow correlation.Alternatively, the processor 50 may take advantage of the narrowcorrelation simply by utilizing the measurements from fewer bins and/orutilizing interpolated values, without changing the sizes of the ranges.

The code generator 24 may also produce a chip transition signal, whichmay be used to assert an enable signal for the complex accumulationregister 36. Following a code chip time in which there is no polaritychange or transition in the locally generated code, for example, a chiptransition signal is asserted and remains asserted for the entire chipto enable the non-transition accumulation register 36 and disable theother registers 34. The chip transition signal is not asserted at thestart of a chip if there is a transition in the local code, and theregister 36 is then disabled, while the registers 34 are enabled as agroup and can then be selected based on the estimated code phase timesof the respective samples. The non-transition complex accumulationregister thus accumulates all of the correlation measurements associatedwith the non-transitioning code chips, and the other registers 34selectively accumulate the measurements associated with the remainingcode chips.

Different discriminator functions may be used at different times duringtracking operations, simply by manipulating the accumulated values fromdifferent groups of bins and/or using different manipulation functions.As discussed earlier, an early-late discriminator function with reducedspacing, that is, narrower correlation, may be used by including asmaller value for n in equation 1, and thus, using the accumulationvalues from fewer “early” and “late” bins. If the tracking loop loseslock, the spacing may be immediately increased by using a larger valuefor n in equation 1, and thus, using the accumulation values from moreof the early and late bins.

Multiple early and/or late values, which correspond to multiple sets ofearly and late correlator hardware in a conventional receiver, may bedetermined at any time by selectively grouping the bins. Accordingly,correlation values that correspond to conventional correlators atlocations that are ½ chip and ¼ chip early, respectively, can be readilydetermined concurrently by selectively combining the contents of theaccumulators to obtain values associated with bins that span the desiredranges—in the example, a ½ chip early value may be produced by$P_{\frac{1}{2}} = {{\sum\limits_{k = {p - 1}}^{N}A_{k}} - {\sum\limits_{k = 1}^{p - 2}A_{k}} + A_{NT}}$while values for ¼ chip spacing may be produced by$P_{\frac{1}{4}} = {{\sum\limits_{k = p}^{N}A_{k}} - {\sum\limits_{k = 1}^{p - 1}A_{k}} + A_{NT}}$and so forth, assuming that bin p-2 begins one-half chip before thedesignated code tracking point and bin p-1 begins one quarter chipbefore the designated code tracking point. The number of correlationvalues and the spacings of the multiple correlation values may bereadily changed by re-grouping and/or re-sizing the bins. Thus, thereceiver may operate as if it includes hardware that consists of anynumber of conventional correlators and/or correlator pairs. Further, thesystem may operate as if the correlators are placed in any number oflocations relative to the correlation peak, and may further operate asif the number, locations and/or spacing of the correlators have changed.Alternatively, or in addition, the receiver may at the same timeselectively group the accumulated measurements to produce thecorrelation values used in blanked correlation and/or other correlationtechniques. Further, the interpolated values may be combined with orused instead of the accumulated values in calculations, to providevalues associated with desired spacing and/or “placement” of thecorrelators.

The accumulated measurements from the respective registers may also beprovided at appropriate times to a multipath mitigation technique (mmt)processor 80 (FIG. 7), which then processes the measurements inaccordance with known multipath mitigation techniques. The multipathmitigation processor thus determines at least an estimate of thelocation of the chip edge of the direct path signal based on theaccumulated pulse shape measurements contained in the array of complexaccumulators. The multipath mitigation processor may also producecarrier tracking and code tracking multipath error signals that are thenused in a conventional manner in the DLL 62 and PLL 60, to removeadverse affects of multipath from the code and carrier trackingoperations.

Referring now also to FIGS. 5B and 7, as an example, the systemaccumulates correlation measurements that correspond to two chips 76 and77 in the local PRN code 75. The bins 72 accumulate measurements thatcorrespond to the duration of a code chip, while the bins 73 accumulatemeasurements that correspond to what are the later contributionsassociated with the same code chip in one or more multipath signals.Thus, the samples taken during local code chip 76 are correlated withthe local code chip 76 and accumulated in bins 72. When the local codetransitions to chip 77, the samples are correlated with, that is,multiplied by, both the local code chip 77 in multiplier 25 and, inmultiplier 25′, the local code chip 76, which is stored in memory 82.The values produced using the local code chip 77 are accumulated in theappropriate bins 72, and the values produced using the stored code chip76 are accumulated in the appropriate bins 73. The bins 73 thus providea shape associated with the ends of the code chips in the receivedmultipath signals. The accumulated values from the bin 72 and 73 maythen be used by the MMT processor 80, to produce an estimate of at leasta direct path signal using the multipath mitigation processingtechniques described above. The MMT processor 80 then provides multipathmitigation signals to the PLL 60 and the DLL 62 through adders 84 and86. The MMT processor 80 may instead operate with accumulated valuesthat correspond to delay spacings of 1 chip or less and/or withinterpolated values.

The code phase decoder 40 and bin processors 43 (FIG. 6) operatetogether to enable the accumulation registers 34 that correspond to theappropriate bins 72 and 73. The bin processors 43 thus enable tworegisters for a given sample, one for the appropriate bin 72 and one forthe appropriate bin 73, when the bins extend beyond 1 chip.

If the bins span three code chips, for example, the system producescorrelation values by multiplying the samples by the current local codechip and stored values of the two previous code chips. The valuesassociated with the current local chip are accumulated in bins 72, thevalues associated with the previous code chip are accumulated in bins 73and the values associated with a second previous chip are accumulated ina set of bins (not shown) that are spaced two chips from bins 72 (onechip from bins 73), and so forth. The bin processors 43 thus operate toenable the appropriate number of bins for each signal sample. Thereceiver does not drive the sample clock to take samples atpre-determined times relative to the estimated code chip boundaries.This allows the receiver to enlarge or reduce the relative sizes ofrespective bins, or ranges, such that samples are spread over more binsor fewer bins, as appropriate, to provide, for example, a more detailedchip edge shape from which to determine the zero crossing or codetracking point and respective early and late correlation values.

The receiver may concurrently produce the different correlationmeasurements that are used in various correlation techniques byselectively grouping the bins. Using appropriately set bin boundaries,the receiver may thus produce from the same set of accumulatedmeasurements the correlation values associated with wide spacing, narrowspacing, blanked correlation, and/or other correlation techniques, aswell as the correlation values associated with various multipathmitigation techniques, such as, for example, the techniques involvingmultiple early and late correlation values.

The foregoing description has been limited to a specific embodiment ofthis invention. It will be apparent, however, that variations andmodifications may be made to the invention, with the attainment of someor all of its advantages. Therefore, it is the object of the appendedclaims to cover all such variations and modifications as come within thetrue spirit and scope of the invention, including sampling the receivedsignal to produce simultaneous I and Q samples. The simultaneous samplesare then processed in parallel, since corresponding I and Q samples willalways occur in the same code chip range or bin. The range or bin sizesmay be fixed and the complex accumulators may be selectively enabled bylogic that is controlled directly by the code phase time values. Theearly measurements, that is, the results of multiplying thedownconverted complex signal and the early version of the local PRNcode, are used for the complex-accumulators 32 in the embodimentdescribed herein. However, the punctual or late measurements may insteadbe used, as long as the edge-detect signal is made synchronous with theselected measurements. The receiver operations may be performed insoftware and/or firmware, is and processors that are depicted separatelymay be combined with other processors and/or individual processors mayinstead consist of multiple processors.

1. A correlation subsystem for a receiver that receives spread-spectrumsignals, including: an array of complex accumulation registers that overmultiple code chips accumulate correlation measurements that correspondto samples of the received signal, the complex accumulators beingassociated with code chip ranges that span all or a portion of one ormore code chips; a code phase decoder that controls the complexaccumulation registers to direct respective correlation measurements tothe complex accumulation registers that are associated with the codechip ranges from which the samples are taken, the code phase decoderdecoding values that correspond to estimated code phase times of thesamples; and a processor for selectively combining the accumulatedvalues from two or more accumulation registers to produce correlationvalues for use in one or more correlation techniques, multipathmitigation techniques or both.
 2. The correlation subsystem of claim 1,wherein the code chip ranges over which the accumulated values arecombined are selected to produce one set or multiple sets of early andlate correlation values.
 3. The correlation subsystem of claim 2,wherein the code chip ranges are adjustable to provide one or moredesired delay spacings.
 4. The correlation subsystem of claim 2 whereinone or all of the sizes, numbers and starting points of the code chipranges are selectively varied to provide one or more desired delayspacings.
 5. The correlation subsystem of claim 2 wherein the processorfurther manipulates the correlation values to produce early minus latecode tracking discriminator information.
 6. The correlation subsystem ofclaim 4 wherein the number of code chip ranges selected for combining isreduced to narrow one or more of the delay spacings.
 7. The correlationsubsystem of claim 4 wherein the number of code chip ranges selected forcombining is increased to widen one or more of the delay spacings. 8.The correlation subsystem of claim 1 wherein a given code range that isassociated with a code tracking point and a number of ranges both beforeand after the given range are selected for combining to determine apunctual correlation value.
 9. The correlation subsystem of claim 8wherein a code error is determined as:$C_{error} = {\frac{{I_{P}I_{E - L}} + {Q_{P}Q_{E - L}}}{I_{P}^{2} + Q_{P}^{2}} \times {chipsize}}$where I and Q are the inphase and quadrature components of the complexvalues.
 10. The correlation subsystem of claim 1 wherein the arrayfurther includes a non-transition complex accumulation register thataccumulates correlation measurements associated with a code chip whenthe code does not transition at a chip time.
 11. The correlationsubsystem of claim 10 wherein a phase error is determined as:${{Phase}\quad{Error}} = {\arctan\quad\left\lbrack \frac{\left( {{\sum\limits_{k = {p + 1}}^{N}I_{k}} - {\sum\limits_{k = 1}^{p}I_{k}} + I_{NT}} \right)^{2}}{\left( {{\sum\limits_{k = {p + 1}}^{N}Q_{k}} - {\sum\limits_{k = 1}^{p}Q_{k}} + Q_{NT}} \right)^{2}} \right\rbrack}$12. The correlation subsystem of claim 10 wherein the punctualcorrelation value is determined as:$P_{p} = {{\sum\limits_{k = {p + 1}}^{N}A_{k}} - {\sum\limits_{k = 1}^{p}A_{k}} + A_{NT}}$where p is the bin that is associated with the code tracking point. 13.A receiver for receiving spread-spectrum signals, the receiverincluding: a local code generator that produces a version of a code thatis included in the received signal; a code phase generator that produceschip edge signals and phase angles that correspond to an estimated codephase; a carrier phase generator that produces phase angles thatcorrespond to an estimated carrier phase; a code tracking delay lockloop that produces code error signals that are used to control the coderate of the code generator; a carrier tracking phase lock loop thatproduces phase error signals that are used to control the carrier phasegenerator; a correlation subsystem that includes an array of complexaccumulation registers that collect measurements that correspond tosamples of the received signal, the accumulators being associated withcode chip ranges that span all or a portion of one or more code chips; acode phase decoder that controls the complex accumulators to direct themeasurements to the respective complex accumulators that are associatedwith the code chip ranges from which the associated samples are taken,the code phase decoder decoding values that correspond to the estimatedphase angles of the samples; and a processor that selectively combinesthe accumulated values from two or more accumulation registers toproduce code tracking discriminator information for the code trackingdelay lock loop.
 14. The receiver of claim 13 wherein the processorfurther selectively combines the accumulated values from various codechip ranges and manipulates the results to produce phase errorinformation for use in the carrier tracking phase lock loop.
 15. Thereceiver of claim 13 further including a multipath mitigation sub-systemfor producing multipath mitigation information for use in code tracking,carrier tracking, or both, and the processor selectively combines theaccumulated values from two or more accumulation registers to producecorrelation values for the multipath mitigation subsystem.
 16. Acomputer generated method for tracking a spread spectrum signal themethod including the steps of: accumulating correlation measurementsthat are associated with samples of a received signal over multiple codechips to produce complex accumulated values that correspond to code chipranges that span all or a portion of one or more code chips; selectivelycombining the complex accumulated values associated with two or morecode chip ranges to produce correlation values for use in one or morecorrelation techniques, one or more multipath mitigation techniques, orboth.
 17. The method of claim 16 further including in the step ofselectively combining the complex accumulated values the step ofselecting the complex accumulated values that combine to produce one ormore early correlation values and one or more late correlation valuesassociated with one or more desired delay spacings.
 18. The method ofclaim 17 further including in the step of producing early and latecorrelation values the step of combining the early and late correlationvalues to produce early minus late discriminator information.
 19. Themethod of claim 18 further including in the step of selectivelycombining the complex accumulated values the step of selectively varyingnumbers of ranges that are combined, sizes of the ranges that arecombined, or both.
 20. The method of claim 16 further including in thestep of selectively combining the complex accumulated values the step ofselecting the complex accumulated values that combine to producecorrelation values that are used to produce code tracking discriminatorinformation.
 21. The method of claim 16 further including in the step ofaccumulating, mathematically manipulating the accumulated values todetermine intermediate values that correspond to ranges that are betweenthe ranges associated with the accumulated values, and in the step ofselectively combining the accumulated values, combining theinter-mediate values instead of or in addition to the accumulatedvalues.